LT6275 Datasheet by Analog Devices Inc.

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ANALOG DEVICES LT6274/LT6275 3” MW 25 \ M ‘ mv 3 Sin 7 _ $ E‘s AV m\ A aw»— 2 {IN Em Av=fl M O 5 v5=g5v mm D mwxmsmmmw \_ mnk w mm mm FREfluENCY VH2)
LT6274/LT6275
1
6275fa
For more information www.linear.com/LT6275
TYPICAL APPLICATION
FEATURES DESCRIPTION
90MHz, 2200V/µs
30V Low Power Op Amps
The LT
®
6274/LT6275 are single/dual low power, high
speed, very high slew rate operational amplifiers with
outstanding AC and DC performance. The circuit topology
is a voltage feedback amplifier with matched high imped-
ance inputs plus the enhanced slewing performance of a
current feedback amplifier. The high slew rate and single
stage design provide excellent settling characteristics that
make the circuit an ideal choice for data acquisition sys-
tems. Each output drives a 1k load to ±13.25V with ±15V
supplies and a 500Ω load to ±3.5V on ±5V supplies. The
LT6274/LT6275 are stable with any capacitive load mak-
ing them useful in buffer or cable driving applications.
The LT6274 single op amp is available in a 5-lead TSOT-23
package, and the LT6275 dual op amp is available in an
8-lead MSOP package. They operate with guaranteed
specifications over the 40°C to 85°C and 40°C to 125°C
temperature ranges.
APPLICATIONS
n 2200V/μs Slew Rate
n 90MHz –3dB Bandwidth (AV = +1)
n 40MHz Gain-Bandwidth Product
n 1.6mA Supply Current per Amplifier
n C-Load™ Op Amp Drives All Capacitive Loads
n ±4.5V to ±16V Operating Supply Range
n Unity-Gain Stable
n 10nV/√Hz Input Noise Voltage
n 400µV Maximum Input Offset Voltage
n 500nA Maximum Input Bias Current
n 30nA Maximum Input Offset Current
n ±13.25V Minimum Output Swing into 1k (±15V Supply)
n ±3.5V Minimum Output Swing into 500Ω (±5V Supply)
n 74dB Minimum Open-Loop Gain, RL = 1k
n 40ns Settling Time to 1%, 10V Step
n Specified at ±5V and ±15V
n Single in 5-Lead TSOT-23 Package
n Dual in 8-Lead MSOP Package
n Wideband Large Signal Amplification
n Cable Drivers
n Buffers
n Automated Test Equipment
n Data Acquisition Systems
n High Fidelity Video and Audio Amplification
All registered trademarks and trademarks are the property of their respective owners. All other
trademarks are the property of their respective owners.
6275 TA01
1k
1k
15V
–15V
VOUT
VIN
AV = –1
FPBW = 3MHz
+
LT627410V
–10V
10V
–10V
Undistorted Output Swing vs Frequency
Wideband Large Signal Amplification
V
S
= ±15V
R
L
= 1k
1% MAX DISTORTION
A
V
A
V
A
V
= –10
FREQUENCY (Hz)
100k
1M
10M
100M
0
5
10
15
20
25
30
OUTPUT VOLTAGE (V
P-P
)
6275 G31
LT6274/LT6275 TOP vwEw A: WU TOP VIEW flflflfl 9% uuuu
LT6274/LT6275
2
6275fa
For more information www.linear.com/LT6275
PIN CONFIGURATION
ABSOLUTE MAXIMUM RATINGS
Total Supply Voltage
(V+ – V) ...................................................................34V
Differential Input Voltage
(Transient Only) (Note 2) ........................................ ±10V
Input Voltage ...................................................... V to V+
Input Current
(+IN, IN) (Note 3) ...............................................±10mA
Output Current (Note 12) ...............................115mARMS
Output Short-Circuit Current Duration
(Note 4) ..........................................Thermally Limited
(Note 1)
ORDER INFORMATION
TUBE TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE
LT6274IS5#PBF LT6274IS5 #TRPBF LTHCY 5-Lead Plastic TSOT-23 –40°C to 85°C
LT6274HS5#PBF LT6274HS5 #TRPBF LTHCY 5-Lead Plastic TSOT-23 –40°C to 125°C
LT6275IMS8#PBF LT6275IMS8 #TRPBF LTFYV 8-Lead Plastic MSOP –40°C to 85°C
LT6275HMS8#PBF LT6275HMS8 #TRPBF LTFYV 8-Lead Plastic MSOP –40°C to 125°C
*The temperature grade is identified by a label on the shipping container.
Consult LTC Marketing for parts specified with wider operating temperature ranges. Parts ending with PBF are RoHS and WEEE compliant.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/. Some packages are available in 500 unit reels through
designated sales channels with #TRMPBF suffix.
http://www.linear.com/product/LT6275#orderinfo
OUT 1
V2
TOP VIEW
S5 PACKAGE
5-LEAD PLASTIC TSOT-23
+IN 3
5 V+
4 –IN
+
θJA = 215°C/W
1
2
3
4
OUTA
–INA
+INA
V
8
7
6
5
V+
OUTB
–INB
+INB
TOP VIEW
MS8 PACKAGE
8-LEAD PLASTIC MSOP
+
+
TJMAX = 150°C, θJA = 163°C/W
Operating Temperature Range (Note 5)
LT6274I/LT6275I ..................................40°C to 85°C
LT6274H/LT6275H ............................. 40°C to 125°C
Specified Temperature Range (Note 6)
LT6274I/LT6275I ..................................40°C to 85°C
LT6274H/LT6275H ............................. 40°C to 125°C
Maximum Junction Temperature .......................... 150°C
Storage Temperature Range .................. 65°C to 150°C
Lead Temperature (Soldering, 10 sec) ...................300°C
LT6274/ LT6275
LT6274/LT6275
3
6275fa
For more information www.linear.com/LT6275
ELECTRICAL CHARACTERISTICS
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
VOS Input Offset Voltage (Note 7)
l
±0.15 ±0.4
±1.2
mV
mV
VOS/∆T Input Offset Voltage Drift (Note 8) l±4 ±10 µV/°C
IBInput Bias Current
l
±100 ±500
±1000
nA
nA
IOS Input Offset Current
l
±3 ±30
±50
nA
nA
enInput Voltage Noise Density f = 1kHz 10 nV/Hz
Low Frequency Integrated Voltage Noise 0.1Hz to 10Hz 1 µVP-P
1/f 1/f Noise Corner Frequency Voltage Noise
Current Noise
30
70
Hz
Hz
inInput Current Noise Density f = 1kHz 0.5 pA/√Hz
RIN Input Resistance Common Mode, VCM = ±12V, VS = ±15V
Differential Mode
l100 700
20
CIN Input Capacitance Common Mode
Differential Mode
3
0.4
pF
pF
VINCM Input Voltage Range + (Note 9) VS = ±15V
VS = ±5V
l
l
12
2.5
13.4
3.4
V
V
Input Voltage Range (Note 9) VS = ±15V
VS = ±5V
l
l
–13.2
–3.2
12
–2.5
V
V
CMRR Common Mode Rejection Ratio VS = ±15V, VCM = ±12V
VS = ±5V, VCM = ±2.5V
l
l
90
80
110
102
dB
dB
PSRR Power Supply Rejection Ratio VS = ±4.5V to ±16V l90 115 dB
VSSupply Voltage Range (Note 10) l9 32 V
Channel Separation VS = ±15V, VOUT = ±1V, AV = 1, RL = 1kΩ l100 126 dB
AVOL Open-Loop Voltage Gain VS = ±15V, VOUT = ±12V, RL = 1kΩ
VS = ±5V, VOUT = ±2.5V, RL = 500Ω
l
l
74
68
90
84
dB
dB
VOUT Maximum Output Voltage Swing ±40mV Input Overdrive
VS = ±15V, RL = 1kΩ
VS = ±5V, RL = 500Ω
l
l
±13.25
±3.5
±13.5
±3.8
V
V
IOUT Output Current VS = ±15V, VOUT = ±12V, VIN = ±40mV
VS = ±5V, VOUT = ±2.5V, VIN = ±40mV
l
l
±15
±12
±35
±30
mA
mA
ISC Output Short-Circuit Current VS = ±15V, VOUT = 0V, VIN = ±3V
VS = ±5V, VOUT = 0V, VIN = ±3V
l
l
±35
±30
±90
±80
mA
mA
ISSupply Current Per Amplifier, VS = ±15V
l
1.6 1.7
2.3
mA
mA
SR Slew Rate (Note 11) VS = ±15V, AV = 1
VS = ±15V, AV = –1
VS = ±15V, AV = –2
VS = ±5V, AV = –2
l
l
900
270
2200
1600
1250
400
V/µs
V/µs
V/µs
V/µs
FPBW Full Power Bandwidth VS = ±15V, 10V Peak, AV = –1, <1% THD
VS = ±5V, 1V Peak, AV = –1, <1% THD
3
8
MHz
MHz
GBW Gain-Bandwidth Product fTEST = 200kHz
VS = ±15V
VS = ±5V
l
l
28
25
40
36
MHz
MHz
f–3dB Unity Gain –3dB Bandwidth VOUT = 100mVP-P, VS = ±15V 90 MHz
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. Unless noted otherwise, VCM = 0V, and specifications apply at both
VS = (V+ – V) = ±5V and ±15V.
LT6274/LT6275
LT6274/LT6275
4
6275fa
For more information www.linear.com/LT6275
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: Differential inputs of ±10V are appropriate for transient operation
only, such as during slewing. Large, sustained differential inputs will
cause excessive power dissipation and may damage the part. See Input
Considerations in the Applications Information section of this data sheet
for more details.
Note 3: The inputs are protected by ESD protection diodes to each power
supply. The Input current should be limited to less than 10mA.
Note 4: A heat sink may be required to keep the junction temperature
below the absolute maximum rating when the output is shorted
indefinitely.
Note 5: The LT6274I/LT6275I are guaranteed functional over the
operating temperature range of –40°C to 85°C. The LT6274H/LT6275H
areguaranteed functional over the operating temperature range of
–40°Cto 125°C.
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. Unless noted otherwise, VCM = 0V, and specifications apply at both
VS = (V+ – V) = ±5V and ±15V.
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
tR, tFSmall Signal Rise/Fall Time AV = 1, 10% – 90%, 100mV Input Step 4 ns
tPD Propagation Delay 50% VIN to 50% VOUT, 100mV Input Step 4 ns
tsSettling Time 1% of 10V Step, AV = 1, VS = ±15V
0.1% of 10V Step, AV = 1, VS = ±15V
1% of 5V Step, AV = 1, VS = ±5V
40
185
65
ns
ns
ns
Note 6: The LT6274I/LT6275I are guaranteed to meet specified
performance from –40°C to 85°C. The LT6274H/LT6275H are guaranteed
to meet specified performance from –40°C to 125°C.
Note 7: Input offset voltage is pulse tested and is exclusive of warm-up drift.
Note 8: This parameter is not 100% tested.
Note 9: Input voltage range is guaranteed by common mode rejection ratio
test.
Note 10: Supply voltage range is guaranteed by power supply rejection
ratio test.
Note 11: Slew rate is measured between 20% and 80% of output step with
±6V input (at AV = –2) and ±10V input (at AV = ±1) for ±15V supplies, and
between 35% and 65% of output step with ±1.75V input (at AV = –2) for
±5V supplies.
Note 12: Current density limitations within the IC require the continuous
RMS current supplied by the output (sourcing or sinking) over the
operating lifetime of the part be limited to under 115mA (Absolute
Maximum). Proper heat sinking may be required to keep the junction
temperature below the absolute maximum rating.
ELECTRICAL CHARACTERISTICS
LT6274/LT6275 3n ‘ 25 125°7 2 ”4* in "‘ i g 25”!) E‘ ,4... {‘5 ’C 3 740”!) 5 __,__".__—— Em "‘ 05 n o 5IuI52o253I735 TOTAL SUPPLV VOLTAGE w) 255 Inn 2 g 5 EN” ‘gqun Eizun 4mm v5=n5v r555 45 rm ,5 n 5 Tu I5 INPUT COMMUN MODEVULTAGE (VI 95 vs=E5v UM E25v an Rl=fiuusz $55 3 \ o :55 3 \\ 75 75 ,50 725 u 25 5o 75 I00 I25 TEMPERATURE m zuu Wu 0 7qu 7200 Esau INPUT UEESET VOLTAGE (W) 7400 V5=:‘5V 7500 45 40 75 U 5 Tu I5 INPUT COMMON MUDE VOLTAGE (V7 400 300 200 mu INPUT EIAS CURRENTmAI 725 n 25 5U 75 TEMPERATURE(“C) I00 I25 I00 95 MM: :IEIEImV 90 85 so 75 UPEN‘LUUP GAIN (Na) 70 55 50 Tu Inn IR Ink LOAD RESISTANCE 1S1) Took TM 7'») PERCENTAGE OF UNITS ( OPEN-LOOP GAIN (HE) V) UUTPUTVULTAGE SWING (2 v5 = 1‘ 5U 35 UNITS 7 uI234557aaIu INPUTOFFSETVOLTAGEDRIFI(WI"CT 95 9L7 75 7U 750 725 n 25 5o 75 TEMPERATURE ("0) I00 I25 I0 I00 IR Wk LOAD RESISTANCE 1S1) Tank 5
LT6274/LT6275
5
6275fa
For more information www.linear.com/LT6275
TYPICAL PERFORMANCE CHARACTERISTICS
Input Bias Current
vs Input Common Mode Voltage Input Bias Current vs Temperature Open-Loop Gain vs Temperature
Open-Loop Gain vs Temperature
Open-Loop Gain
vs Resistive Load
Output Voltage Swing
vs Resistive Load
Supply Current vs Supply Voltage
and Temperature (per Amplifier)
Input Offset Voltage vs Input
Common Mode Voltage
Typical Distribution of Input
Offset Voltage Drift
25°C
125°C
–40°C
TOTAL SUPPLY VOLTAGE (V)
0
5
10
15
20
25
30
35
0
0.5
1.0
1.5
2.0
2.5
3.0
SUPPLY CURRENT (mA)
6275 G01
25°C
125°C
–40°C
V
S
= ±15V
INPUT COMMON MODE VOLTAGE (V)
–15
–10
–5
0
5
10
15
–500
–400
–300
–200
–100
0
100
200
INPUT BIAS CURRENT (nA)
6275 G04
V
S
= ±15V
TEMPERATURE (°C)
–50
–25
0
25
50
75
100
125
0
100
200
300
400
INPUT BIAS CURRENT (nA)
6275 G05
V
S
= ±15V
V
OUT
= ±12V
R
L
= 1k
TEMPERATURE (°C)
–50
–25
0
25
50
75
100
125
70
75
80
85
90
95
OPEN-LOOP GAIN (dB)
6275 G06
V
S
= ±5V
V
OUT
= ±2.5V
R
L
= 500Ω
TEMPERATURE (°C)
–50
–25
0
25
50
75
100
125
70
75
80
85
90
95
OPEN-LOOP GAIN (dB)
6275 G07
V
S
= ±5V
V
S
= ±15V
T
A
= 25°C
V
OUT
= ±100mV
LOAD RESISTANCE (Ω)
10
100
1k
10k
100k
1M
60
65
70
75
80
85
90
95
100
OPEN-LOOP GAIN (dB)
6275 G08
V
S
= ±15V
V
IN
= ±20mV
T
A
= 25°C
LOAD RESISTANCE (Ω)
10
100
1k
10k
100k
0
2
4
6
8
10
12
14
16
OUTPUT VOLTAGE SWING (±V)
6275 G09
25°C
125°C
–40°C
V
S
= ±15V
INPUT COMMON MODE VOLTAGE (V)
–15
–10
–5
0
5
10
15
0
100
200
INPUT OFFSET VOLTAGE (µV)
6275 G02
V
S
= ±15V
36 UNITS
INPUT OFFSET VOLTAGE DRIFT (µV/°C)
0
1
2
3
4
5
6
7
8
9
10
0
5
10
15
20
25
30
35
PERCENTAGE OF UNITS (%)
6275 G03
LTé2 74/ LT6275 0mm VOLTAGE sww NE (le m mu m Wk mm: RES‘STANCE an a < ourpur="" voltage="" swwts="" m="" 750="" an="" an="" ,m="" 4n="" n="" 0mm="" currenhmr)="" w="" wputvultage="" nmse="" an‘v‘hn="" ‘="" m="" ion="" ik="" mx="" rmumcv="" um="" max="" m="" 20="" an="" an="" an="" mu="" m="" m="" max="" uh="" whskjn="" mauammdm="" max="" rl="" ,="" 5mm="" ru="" 5mm="" ourpur="" voltage="" swwts="" m="" erw="" u="" sm‘fizuzfiauas="" mm="" suppw="" voltage="" wi="" ourpur="" voltage="" swwts="" va="" isniwiaurzurm="" u="" m="" 2n="" an="" an="" an="" uuwurcumwumn)="" nu="" ‘="" mm="" h="" h="" vsrgsv="" e="" swx="" e="" ‘="" ‘="" vwriav="" emu="" 5="" an="" scum="" e="" \="" e="" a="" an="" \="" a="" an="" é="" scum="" \\="" g="" ;:="" an="" e="" m="" é="" 7n="" é="" an="" an="" 5m="" 750="" 725="" u="" 25="" 5d="" 75="" um="" 125="" rwpmmm-c)="" wputvultaee="" nmse="" lzddnv/dw}="" nmeus/mw="" "m="" 750="" 725="" u="" 25="" 5d="" 75="" um="" 125="" rwpmmm-c)="" 25m="" mm="" mm="" mm="" swune="" 1me="" ms)="" 5n="" 2="" a="" s="" s="" m="" ouwursrgpm="">
LT6274/LT6275
6
6275fa
For more information www.linear.com/LT6275
TYPICAL PERFORMANCE CHARACTERISTICS
Settling Time vs Output Step
Output Short-Circuit Current
vs Temperature
Output Short-Circuit Current
vs Temperature
Input Noise Spectral Density
0.1Hz to 10Hz
Input Voltage Noise
Output Voltage Swing
vs Resistive Load
Output Voltage Swing
vs Supply Voltage
Output Voltage Swing
vs Load Current
Output Voltage Swing
vs Load Current
V
S
= ±5V
V
IN
= ±20mV
T
A
= 25°C
LOAD RESISTANCE (Ω)
10
100
1k
10k
100k
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
OUTPUT VOLTAGE SWING (±V)
6275 G10
R
L
= 1k
R
L
= 1k
R
L
= 500Ω
R
L
= 500Ω
V
IN
= ±20mV
TOTAL SUPPLY VOLTAGE (V)
0
5
10
15
20
25
30
35
V
1
2
3
–3
–2
–1
V
+
OUTPUT VOLTAGE SWING (V)
6275 G11
TA = ±25°C
V
S
= ±15V
V
IN
= ±20mV
125°C
125°C
–40°C
–40°C
25°C
25°C
OUTPUT CURRENT (mA)
–50
–40
–30
–20
–10
0
10
20
30
40
50
V
1
2
3
–3
–2
–1
V
+
OUTPUT VOLTAGE SWING (V)
6275 G12
V
S
= ±5V
V
IN
= ±20mV
125°C
125°C
–40°C
–40°C
25°C
25°C
OUTPUT CURRENT (mA)
–50
–40
–30
–20
–10
0
10
20
30
40
50
V
1
2
3
–3
–2
–1
V
+
OUTPUT VOLTAGE SWING (V)
6275 G13
V
S
= ±15V
V
IN
= ±3V
SOURCE
SINK
TEMPERATURE (°C)
–50
–25
0
25
50
75
100
125
60
70
80
90
100
110
OUTPUT SHORT-CIRCUIT CURRENT (mA)
6275 G14
V
S
= ±5V
V
IN
= ±3V
SOURCE
SINK
TEMPERATURE (°C)
–50
–25
0
25
50
75
100
125
50
60
70
80
90
100
OUTPUT SHORT-CIRCUIT CURRENT (mA)
6275 G15
e
n
i
n
FREQUENCY (Hz)
1
10
100
1k
10k
100k
1
10
100
1k
0.1
1
10
100
INPUT VOLTAGE NOISE (nV/√
Hz
)
INPUT CURRENT NOISE (pA/√
Hz
)
6275 G16
V
S
= ±15V
V
S
= ±15V
TIME (1s/DIV)
INPUT VOLTAGE NOISE (200nV/DIV)
6275 G17
V
S
= ±15V
A
V
= 1
R
L
= 2k
0.1%
1%
OUTPUT STEP (V)
2
4
6
8
10
0
50
100
150
200
250
SETTLING TIME (ns)
6275 G18
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LT6274/LT6275
7
6275fa
For more information www.linear.com/LT6275
Closed-Loop Output Impedance
vs Frequency Gain/Phase vs Frequency
Gain-Bandwidth Product and
Phase Margin vs Temperature
Gain-Bandwidth Product
and Phase Margin
vs Supply Voltage
TYPICAL PERFORMANCE CHARACTERISTICS
Power Supply Rejection Ratio
vs Frequency
Closed-Loop Frequency
Response vs Load Capacitance
Closed-Loop Frequency
Response vs Load Capacitance
Crosstalk vs Frequency
V
S
= ±15V
T
A
= 25°C
A
V
= 1
A
V
= 10
A
V
= 100
FREQUENCY (Hz)
100
1k
10k
100k
1M
10M
100M
0.01
0.1
1
10
100
1k
OUTPUT IMPEDANCE (Ω)
6275 G20
PHASE
GAIN
V
S
= ±5V
V
S
= ±15V
T
A
= 25°C
FREQUENCY (Hz)
10k
100k
1M
10M
100M
1G
–20
–10
0
10
20
30
40
50
60
70
80
–210
–180
–150
–120
–90
–60
GAIN (dB)
PHASE (DEG)
6275 G21
PHASE MARGIN
V
S
= ±5V
PHASE MARGIN
V
S
= ±15V
GAIN-BANDWIDTH PRODUCT
V
S
= ±15V
GAIN-BANDWIDTH PRODUCT
V
S
= ±5V
TEMPERATURE (°C)
–50
–25
0
25
50
75
100
125
30
35
40
45
50
55
60
30
35
40
45
50
55
60
GAIN-BANDWIDTH PRODUCT (MHz)
PHASE MARGIN (DEG)
6275 G22
PHASE MARGIN
GAIN-BANDWIDTH PRODUCT
T
A
= 25°C
TOTAL SUPPLY VOLTAGE (V)
0
5
10
15
20
25
30
35
30
35
40
45
50
55
60
30
35
40
45
50
55
60
GAIN-BANDWIDTH PRODUCT (MHz)
PHASE MARGIN (DEG)
6275 G23
V
S
= ±15V
T
A
= 25°C
A
V
= 1
C = 0
C = 50pF
C = 100pF
C = 500pF
C = 10nF
C = 5nF
C = 1nF
FREQUENCY (Hz)
100k
1M
10M
100M
1G
–20
–10
0
10
GAIN MAGNITUDE (dB)
6275 G24
V
S
= ±5V
T
A
= 25°C
A
V
= 1
C = 0
C = 50pF
C = 100pF
C = 500pF
C = 10nF
C = 5nF
C = 1nF
FREQUENCY (Hz)
100k
1M
10M
100M
1G
–20
–10
0
10
GAIN MAGNITUDE (dB)
6275 G25
T
A
= 25°C
A
V
= 1
V
IN
= 2V
P–P
V
S
= ±15V
R
L
= 1k
V
S
= ±5V
R
L
= 500Ω
FREQUENCY (Hz)
10k
100k
1M
10M
100M
–130
–120
–110
–100
–90
–80
–70
–60
–50
CROSSTALK (dB)
6275 G26
V
S
= ±15V
T
A
= 25°C
PSRR
+PSRR
FREQUENCY (Hz)
100
1k
10k
100k
1M
10M
100M
–20
0
20
40
60
80
100
120
POWER SUPPLY REJECTION RATIO (dB)
6275 G27
Common Mode Rejection Ratio
vs Frequency
V
S
= ±15V
T
A
= 25°C
FREQUENCY (Hz)
100
1k
10k
100k
1M
10M
100M
0
20
40
60
80
100
120
COMMON MODE REJECTION RATIO (dB)
6275 G28
LTé2 74/ LT6275 HARMONIC DISTURTIUN (118:) OUTPUT VOLTAGE (vp p) 30 3 25 E é: 20 E é E E ‘5 3RD HARMON‘C 3 3’70 HARMONIC i E § In E 5 A\( = n 5 END HARMOMC D 2ND HARMONIC I 5 Vs=1‘5V Kl = ‘k n ""n MAX D‘STORTION \ IUD ‘k IUK ‘UUk ‘M IUM IUD ‘k IUK ‘UUk ‘M IUM IUUK ‘M IUM ‘UUM EPEUUEch (Hz) , EPEUUEch (Hz) , EPEUUEch (Hz) ‘0 2500 ‘ ‘ ‘ ‘ 2500 ‘ ‘ ‘ OUTPUT FALL‘NG 8 VS 1 4 SU ouTPUT FALL‘NG a 2000 m. mm ,7 ' 2000 v5 , 15v Av=o‘ 20 m 8" OFSTEP :‘ZV OUTPUT STEP $ 3 // 5 6 I500 a ‘500 w w § § OUTPUT PISTNS a E 1an 7 E woo V5=:‘5V i a OUTPUT “‘5‘“; d sz DuTPUT STEP // vs = mv 2 500 r f 500 L // V: = M n ""n MAX D‘STORTION . n / Vs = :5v 0 :3 5v ouTPUT STEP IUUK ‘M ‘UM IUUM U 2 4 5 8 ‘U ‘2 ‘4 ‘6 I8 20 *50 *25 U 25 50 75 ‘00 ‘25 FREQUENCV (Hz) , WPUT LEVEL (vw) , TEMPERATURE (TC) ‘0000 EU v5 = :‘SV 70 IUUNV STEP ‘000 50 S (on k 5" t g 40 P i ‘0 § 30 .,, a ‘ v5 = :‘SV 20 AV: 4 RC, = n; = 2x (a ‘ 20% ‘0 EUE’D 0‘ :‘UV STEP U G ‘p ‘09 ‘UUD ‘77 Inn ‘00” ‘U ‘09 ‘UUD ‘fl ‘0” ‘UUH ‘U LOAD CAPAC‘TANCE (E) LOAD CAPAC‘TANCE (E)
LT6274/LT6275
8
6275fa
For more information www.linear.com/LT6275
TYPICAL PERFORMANCE CHARACTERISTICS
Slew Rate vs Capacitive Load
Step Response Overshoot
vs Capacitive Load
Slew Rate vs Input Level Slew Rate vs Temperature
2nd and 3rd Harmonic Distortion
vs Frequency (AV = 1)
2nd and 3rd Harmonic Distortion
vs Frequency (AV = –1)
Undistorted Output Swing
vs Frequency
Undistorted Output Swing
vs Frequency
V
S
= ±15V
V
IN
= 10V
P–P
R
L
= 1k
2ND HARMONIC
3RD HARMONIC
FREQUENCY (Hz)
100
1k
10k
100k
1M
10M
–140
–130
–120
–110
–100
–90
–80
–70
–60
–50
–40
–30
–20
HARMONIC DISTORTION (dBc)
6275 G29
V
S
= ±15V
V
IN
= 10V
P–P
R
G
= R
F
= 1k
2ND HARMONIC
3RD HARMONIC
FREQUENCY (Hz)
100
1k
10k
100k
1M
10M
–90
–80
–70
–60
–50
–40
–30
–20
HARMONIC DISTORTION (dBc)
6275 G30
V
S
= ±15V
R
L
= 1k
1% MAX DISTORTION
A
V
A
V
A
V
= –10
FREQUENCY (Hz)
100k
1M
10M
100M
0
5
10
15
20
25
30
OUTPUT VOLTAGE (V
P-P
)
6275 G31
V
S
= ±5V
R
L
= 1k
1% MAX DISTORTION
A
V
A
V
= –10
A
V
FREQUENCY (Hz)
100k
1M
10M
100M
0
2
4
6
8
10
OUTPUT VOLTAGE (V
P-P
)
6275 G32
OUTPUT FALLING
V
S
= ±15V
OUTPUT RISING
V
S
= ±15V
T
A
= 25°C
A
V
R
G
= R
F
= 2k
20% to 80% OF STEP
V
S
= ±5V
INPUT LEVEL (V
P-P
)
0
2
4
6
8
10
12
14
16
18
20
0
500
SLEW RATE (V/µs)
6275 G33
OUTPUT FALLING
V
S
= ±15V
±12V OUTPUT STEP
OUTPUT RISING
V
S
= ±15V
±12V OUTPUT STEP
A
V
R
G
= 2k, R
F
= 4k
20% to 80% OF STEP
V
S
= ±5V
±3.5V OUTPUT STEP
TEMPERATURE (°C)
–50
–25
0
25
50
75
100
125
0
500
SLEW RATE (V/µs)
6275 G34
V
S
= ±15V
A
V
R
G
= R
F
= 2k
20% to 80% of ±10V STEP
LOAD CAPACITANCE (F)
1p
10p
1n
10n
0.1
1
10
100
10000
SLEW RATE (V/µs)
6275 G35
A
V
= –1
R
G
= R
F
= 2k
A
V
= 1
V
S
= ±15V
100mV STEP
LOAD CAPACITANCE (F)
10p
1n
10n
0
10
20
30
40
50
60
70
80
OVERSHOOT (%)
6275 G36
zan/Dlv EV/DIV ZDHS’DIV EDns’DIV zan/Dlv EV/DIV ZUns/D w EDns’DIV zan/Dlv EV/DIV LT6274/ LTé275 snunsmv EUS’DIV
LT6274/LT6275
9
6275fa
For more information www.linear.com/LT6275
Small-Signal Step Response
(AV = 1)
Small-Signal Step Response
(AV = –1)
Small-Signal Step Response
(AV = 1, CL = 10nF)
TYPICAL PERFORMANCE CHARACTERISTICS
Large-Signal Step Response
(AV = 1)
Large-Signal Step Response
(AV = –1)
Large-Signal Step Response
(AV = 1, CL = 10nF)
V
S
= ±15V
20ns/DIV
20mV/DIV
6275 G37
V
S
= ±15V
R
G
= R
F
= 2k
20ns/DIV
20mV/DIV
6275 G38
V
S
= ±15V
500ns/DIV
20mV/DIV
6275 G39
V
S
= ±15V
50ns/DIV
5V/DIV
6275 G40
V
S
= ±15V
R
G
= R
F
=2k
50ns/DIV
5V/DIV
6275 G41
V
S
= ±15V
5µs/DIV
5V/DIV
6275 G42
LT6274/LT6275 '3 a a $46 3—K WWW; DE?- $9 *1 ‘IO
LT6274/LT6275
10
6275fa
For more information www.linear.com/LT6275
SIMPLIFIED SCHEMATIC
(ONE AMPLIFIER SHOWN)
6275 SS01
OUT
+IN
–IN
V+
V
R1
1k
CC
RC
C
LT6274/ LT6275 ‘I‘I
LT6274/LT6275
11
6275fa
For more information www.linear.com/LT6275
PIN FUNCTIONS
–IN: Inverting Input of Amplifier.
+IN: Noninverting Input of Amplifier.
V+: Positive Supply Voltage. Total supply voltage (V+ V)
ranges from 9V to 32V.
V: Negative Supply Voltage. Total supply voltage
(V+–V) ranges from 9V to 32V.
OUT: Amplifier Output.
LT6274/LT6275 12
LT6274/LT6275
12
6275fa
For more information www.linear.com/LT6275
Circuit Operation
The LT6274/LT6275 circuit topology is a true voltage
feedback amplifier that has the slewing behavior of a cur-
rent feedback amplifier. The operation of the circuit can
be understood by referring to the simplified schematic.
The inputs are buffered by complementary NPN and PNP
emitter followers that drive a 1k resistor. The input voltage
appears across the resistor generating currents that are
mirrored into the high impedance node. Complementary
followers form an output stage that buffers the gain node
from the load. The bandwidth is set by the internal input
resistor and the capacitance on the high impedance node.
The slew rate is determined by the current available to
charge the gain node capacitance. This current is the dif-
ferential input voltage divided by R1, so the slew rate is
proportional to the input. This important characteristic
gives the LT6274/LT6275 superior slew performance
compared to conventional voltage feedback amplifiers in
which the slew rate is constrained by a fixed current (bias-
ing the input transistors) available to charge the gain node
capacitance (independent of the magnitude of the differen-
tial input voltage). Therefore, in the LT6274/LT6275, high-
est slew rates are seen in the lowest gain configurations.
For example, a 10V output step in a gain of 10 has only a
1V input step, whereas the same output step in unity gain
has a 10 times greater input step. The curve of Slew Rate
vs Input Level illustrates this relationship. The LT6274/
LT6275 are tested in production for slew rate in a gain of
2 so higher slew rates can be expected in gains of 1 and
1, with lower slew rates in higher gain configurations.
Special compensation across the output buffer allows the
LT6274/LT6275 to be stable with any capacitive load. The
RC network across the output stage is bootstrapped when
the amplifier is driving a light or moderate load and has
no effect under normal operation. When driving a capaci-
tive load (or a low value resistive load) the network is
incompletely bootstrapped and adds to the compensa-
tion at the high impedance node. The added capacitance
slows down the amplifier by lowering the dominant pole
frequency, improving the phase margin. The zero created
by the RC combination adds phase to ensure that even
for very large load capacitances, the total phase lag does
not exceed 180° (zero phase margin), and the amplifier
remains stable.
APPLICATIONS INFORMATION
Comparison to Current Feedback Amplifiers
The LT6274/LT6275 enjoy the high slew rates of Current
Feedback Amplifiers (CFAs) while maintaining the char-
acteristics of a true voltage feedback amplifier. The pri-
mary differences are that the LT6274/LT6275 have two
high impedance inputs, and the closed loop bandwidth
decreases as the gain increases. CFAs have a low imped-
ance inverting input and maintain relatively constant
bandwidth with increasing gain. The LT6274/LT6275 can
be used in all traditional op amp configurations including
integrators and applications such as photodiode ampli-
fiers and I-to-V converters where there may be significant
capacitance on the inverting input. The frequency com-
pensation is internal and does not depend on the value
of the external feedback resistor
. For CFAs, by contrast,
the feedback resistance is fixed for a given bandwidth,
and capacitance on the inverting input can cause peaking
or oscillations. The slew rate of the LT6274/LT6275 in
noninverting gain configurations is also superior to that
of CFAs in most cases.
Input Considerations
Each of the LT6274/LT6275 inputs is the base of an NPN
and a PNP transistor whose base currents are of opposite
polarity and provide first-order input bias current cancel-
lation. Because of differences between NPN and PNP beta,
the polarity of the input bias current can be positive or
negative. The offset current does not depend on NPN/PNP
beta matching and is well controlled. The use of balanced
source resistance at each input is therefore recommended
for applications where DC accuracy must be maximized.
The inputs can withstand transient differential input volt-
ages up to ±10V without damage and need no clamping
or source resistance for protection. Differential inputs,
however, generate large supply currents (tens of mA) as
required for high slew rates. If the device is used with
sustained differential inputs, the average supply current
will increase, excessive power dissipation will result, and
the part may be damaged. The part should not be used
as a comparator, peak detector or in other open-loop
applications with large, sustained differential inputs.
Under normal, closed-loop operation, an increase of
power dissipation is only noticeable in applications with
LT6274/ LT6275 13
LT6274/LT6275
13
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For more information www.linear.com/LT6275
large slewing outputs, and the increased power is propor-
tional to the magnitude of the differential input voltage and
the percent of the time that the inputs are apart. Measure
the average supply current for the application in order to
calculate the power dissipation.
Capacitive Loading
The LT6274/LT6275 are stable with any capacitive load.
As previously stated in the Circuit Operation section of this
data sheet, this is accomplished by dynamically sensing
the load-induced output pole and adjusting the compensa-
tion at the amplifiers internal gain node. As the capacitive
load increases, the bandwidth will decrease. The phase
margin may increase or decrease with different capaci-
tive loads, and so there may be peaking in the frequency
domain and overshoot in the transient response for some
capacitive loads as shown in the Typical Performance
curves. The Small-Signal Step Response curve with 10nF
load shows 30% overshoot. For large load capacitance,
the slew rate of the LT6274/LT6275 can be limited by
the output current available to charge the load capacitor
according to:
SR =
I
SC
CL
The Large-Signal Step Response with 10nF load shows
the output slew rate being limited to 9V/µs by the output
short-circuit current. Coaxial cable can be driven directly,
but for best pulse fidelity the cable should be properly
terminated by placing a resistor of value equal to the char-
acteristic impedance of the cable (e.g. 50Ω) in series with
the output. The other end of the cable should be termi-
nated with the same value resistor to ground.
Layout and Passive Components
The LT6274/LT6275 are easy to use and tolerant of less
than ideal layouts. For maximum performance use a
ground plane, short lead lengths, and RF-quality ceramic
bypass capacitors (0.01µF to 0.1µF). For high drive cur-
rent applications use low ESR bypass capacitors (1µF to
10µF ceramic or tantalum). The resistance of the parallel
combination of the feedback resistor and gain setting
resistor on the inverting input combines with the total
capacitance on that node, CIN, to form a pole which can
cause peaking or oscillations. If feedback resistors greater
than 5k are used, a parallel capacitor of value
CF > RG × CIN/RF
should be used to cancel the input pole and optimize
dynamic performance. For unity-gain applications where
a large feedback resistor is used, C
F
should be greater
than or equal to CIN.
Power Dissipation
The LT6274/LT6275 combine high speed and large out-
put drive in a small package. Because of the wide sup-
ply voltage range, it is possible to exceed the maximum
junction temperature under certain conditions. Maximum
junction temperature (TJ) is calculated from the ambient
temperature (T
A
), the devices power dissipation (P
D
),
and the thermal resistance of the device (θJA) as follows:
TJ = TA + (PD × θJA)
Worst case power dissipation occurs at the maximum
supply current and when the output voltage is at 1/2 of
either V+ or V (on split rails), or at the maximum out-
put swing (if less than 1/2 of the rail voltage). Therefore
PDMAX (per amplifier) is:
PDMAX = (V+ – V)(ISMAX) + (V+/2)2/RL
Example: For an LT6274 with thermal resistance of
215°C/W, operating on ±15V supplies and driving a 1kΩ
load to 7.5V, the maximum power dissipation is calculated
to be:
PDMAX = (30V)(2.3mA) + (7.5V)2/1kΩ = 125mW
This leads to a die temperature rise above ambient of:
TRISE = (125mW)(215°C/W) = 27°C
This implies that the maximum ambient temperature at
which the LT6274 should operate under the above condi-
tions is:
TA = 150°C – 27°C = 123°C
APPLICATIONS INFORMATION
LTé274/LT6275 OUTFUTVOLTAGE (w a EDns’DW 14
LT6274/LT6275
14
6275fa
For more information www.linear.com/LT6275
TYPICAL APPLICATIONS
Noninverting Amplifier Slew Rate and Step Response
Figure 1 shows a noninverting amplifier with closed-loop
gain of 11V/V. The closed-loop bandwidth of this ampli-
fier is approximately GBW/11 (GBW = Gain-Bandwidth
Product). For a step input, the output follows an expo-
nential curve:
VOUT =V
INITIAL +AV• V
INPUTSTEP 1– e
t
τ
(1)
where τ = time constant associated with the closed-loop
bandwidth.
The maximum slew rate occurs in the beginning of the
output response:
VOUTSRMAX =AV• V
INPUSTEP
1
τ
(2)
Keep in mind that the closed-loop bandwidth and the
closed-loop gain are related (τ = τo AV), so Equation (2)
is simplified to:
VOUTSRMAX =V
INPUTSTEP
1
τo
(3)
where τ
o
= time constant associated with the LT6274/
LT6275 GBW.
Interestingly, Equation (3) reveals that the maximum slew
rate is nominally related only to the input step size and the
op amps inherent GBW. Closing the loop to implement
AV > 1 gain configurations slows down the response, but
increases the excursion. The resulting maximum slew rate
remains the same.
The LT6274/LT6275 feature ample slew rate capability
with low power consumption. Because the input stage
architecture allows high slew rate with low input stage
quiescent currents, the overall power consumption when
amplifying pulses is very low; additional power is only
drawn from the supplies during the highest slew rate
moments of the exponential response.
Since GBW of the LT6274/LT6275 is 40MHz, Equation (3)
suggests that the maximum slew rate in a step response
whose output swings 25V (implying VINPUTSTEP = 25/11
= 2.27V) is 571V/µs. The LT6274/LT6275 high slew
capability ensures that the output response is never slew
rate limited despite the very high excursion.
Figure 2 shows the output response to varying input step
amplitudes. Note that none of the exponential responses
is limited by the initial slew rate (which increases with
increasing amplitude).
As a particular example, with A
V
= +11V/V, 15V output
excursion, and 40 MHz GBW, Equation (3) predicts a
maximum slew rate of 343V/μs. Measurement on the cor-
responding curve in Figure 2 shows 390V/μs, which is in
good agreement with the prediction. As another example,
with an 18.5V output excursion, the predicted maximum
slew rate is 423V/μs; measurement shows 460V/μs.
As the peak to peak voltage of the input step changes, the
maximum initial slew rate changes. The 63% rise time
of the closed loop response, however, does not change
(as seen in Figure 2), because the closed loop bandwidth
stays constant for all input amplitudes.
R
F
2k
6275 TA06
R
G
200
1/2 LT6275
+15V
–15V
V
IN
V
OUT
A
V
= +11
50ns/DIV
–15
–12
–9
–6
–3
0
3
6
9
12
15
OUTPUT VOLTAGE (V)
6275 TA07
Figure 1. LT6275 Configured in a Noninverting Gain of AV = +11V/V
Figure 2. Noninverting Amplifier Step Response (AV = +11V/V)
LT6274/ LT6275 R4 07 m —RJ '— 2k 39 w usv 32 , W 5v — 1/2 mm —| Vow v LTCEZEZ + R; 4 5V V Elk + 15
LT6274/LT6275
15
6275fa
For more information www.linear.com/LT6275
TYPICAL APPLICATIONS
Using the LT6274/LT6275 to Create a Composite
Amplifier with High Gain, High Bandwidth and Large
Output Signal Capability
While the LT6274/LT6275 provide ample slew rate and
large output swing capability, the GBW is not so large
as to achieve high gain, high bandwidth, and high ampli-
tude at the same time. The circuit of Figure 3 harnesses
the high slew rate capability of the LT6275 by placing it
under control of the LTC6252, an op amp with greater
than 700MHz GBW. The LT C6252 offers high bandwidth
at low supply current, but with limited slew rate and lim-
ited output swing (since it is a 5V op amp). By creating a
composite amplifier adding the LT6275 as a high-voltage,
high-slew secondary op amp, this composite amplifier
enables large output swing at high frequencies with rela-
tively low power dissipation.
Circuit Description
R4 and R1 realize inverting gain of –11V/V from VIN to
V
OUT
. The LT6275 op amp drives the output based on
whatever is commanded by the middle node, VMID. The
LTC6252 is very fast relative to the LT6275. As a conse-
quence, the LTC6252 controlling first stage can force the
LT6275 output to move quickly by providing sufficient
differential input voltage to the LT6275. With the inverting
input of the LT6275 tied to a DC bias voltage, the LTC6252
needs merely to drive the noninverting input.
Unlike the LTC6252, the LT6275 slew rate increases lin-
early with its differential input voltage. Hence, the LTC6252
benefits from using the LT6275 as a slew enhancer.
Optimizing the Loop
Larger R2 increases the local gain taken by the LTC6252.
Since the total gain is fixed by the global feedback around
the composite amplifier (AV = –R4/R1 = –11V/V), raising
the gain in the LTC6252 lowers the gain requirement of
the LT6275, increasing the overall bandwidth of the com-
posite amplifier. Care must be taken to not take too much
gain in the LTC6252, as the reduction in the LTC6252
bandwidth and the resulting additional phase shift seen
at the output of the LTC6252 can lower the stability mar-
gins of the composite amplifier. Conversely, smaller R2
VMID
6275 TA08
R
4
11k
C
5
R
6
10k
R
5
10k
R
1
1k
C
1
C
2
R
3
10k
R
2
2k
C
7
3p
1/2 LT6275
+15V
–15V
V
IN
V
OUT
LTC6252
5V
5V
reduces the LTC6252 phase shift, but it also adds to the
gain burden of the LT6275.
R2 was selected to take a gain of 2V/V in the LTC6252,
implying a gain of 5.5V/V being taken in the LT6275. The
5.5V/V gain is required to translate the 5V maximum out-
put swing of the LTC6252 to the 27.5V maximum output
swing of the LT6275 (when operated at ±15V supplies). It
may be possible to achieve even higher bandwidth in the
composite amplifier if a high speed ±5V (rather than 5V,
0V) op amp replaces the LTC6252 as the first stage, with
the resulting increased first-stage output swing lowering
the gain that has to be taken in the LT6275.
Capacitor C7 in Figure 3 is adjusted to create a favorable
looking transient response. Figure 4 shows the transient
response at the output of the LT6275 as C7 varies. C7 =
3pF was chosen.
DC Biasing
In the circuit of Figure 3, LTC6252 supplies were cho-
sen to be 5V and 0V, which are more practical than split
±2.5V supplies. R5 and R6 form a resistive divider to
bias the noninverting input of LTC6252 and the inverting
input of LT6275 at the middle of this rail, 2.5V. Note that
this approach results in the output of LT6275 having a DC
offset of 2.5V, which reduces the potential peak to peak
output excursion of the composite amplifier since LT6275
is powered up from split ±15V supplies.
Figure 3. Composite Amplifier Using
LTC6252 and LT6275 (AV = –11V/V)
LTé274/LT6275 OUTPUT VOLTAGE (V) znunsxmv n-svm 225 ‘80 ‘35 90 45 E a I c. ’45 E ’90 435 — SAW 4m, —— PHASE ,225 [I ‘ V W WEI FREDUENCHMHZ) 5 ‘50 USWG V2 LT5275 g A ‘ ‘20 “ E 3 £3 a 3 E .— ' x/ E k I "’ // )1 a a ___,.. f , g S 5 2 60 g 0 & _” ' v a — 5v SUPPLY CURRENT ‘ —— nsv sumv CURRENT, 30 — — mm POWER zsunsxmv ’2‘“ n OUTPUT = 2w” 0 [I 5 ‘ V 5 2 mmummmm 16
LT6274/LT6275
16
6275fa
For more information www.linear.com/LT6275
TYPICAL APPLICATIONS
Pulse Response
Figure 5 shows the output step response of the composite
amplifier (measured at the output of the LT6275) at many
different amplitudes. At 15V output excursion, the initial
slope is measured to be 725V/μs. This slope is faster than
the 390V/μs measured with a 15V output excursion using
the simple noninverting amplifier of Figure 1. According
to Equation (3), this improvement has been made pos-
sible because the effective bandwidth of the composite
amplifier is higher (and thus has a lower τo), as intended.
Sine Waves
The composite amplifier of Figure 3 was also tested with
sine waves. Figure 6 shows the small signal closed-loop
gain and phase response. Distortion was also evaluated
for this circuit: for a 20VP-P output signal at 1MHz, HD2/
HD3 were measured to be –55dBc/–47dBc, respectively.
These numbers are more impressive when consider-
ing the very low power dissipation of the composite
amplifier, as illustrated in Figure 7. For example, for the
20VP-P/1MHz output condition mentioned above, the 5V
rail supply current is 3.75mA, for 1/2 LT6275 the ±15V
rails supply current is 2.2mA, resulting in a total power
dissipation of 85mW.
8pF
5pF
3pF
1pF
NO CAP
250ns/DIV
–10
–8
–6
–4
–2
0
2
4
6
8
10
OUTPUT VOLTAGE (V)
6275 TA09
Figure 4. Composite Amplifier Step Response
vs LTC6252 Feedback Capacitance (AV = –11V/V)
Figure 5. Composite Amplifier Step Response at
Various Output Step Amplitudes (AV = –11V/V)
200ns/DIV
–15
–12
–9
–6
–3
0
3
6
9
12
15
OUTPUT VOLTAGE (V)
6275 TA12
GAIN
PHASE
FREQUENCY (MHz)
0.1
1
10
100
–25
–20
–15
–10
–5
0
5
10
15
20
25
–90
–45
0
45
90
135
180
225
GAIN (dB)
PHASE (DEG)
6275 TA14
USING 1/2 LT6275
OUTPUT = 20V
P–P
5V SUPPLY CURRENT
±15V SUPPLY CURRENT
TOTAL POWER
FREQUENCY (MHz)
0
0.5
1
1.5
2
0
1
2
3
4
5
0
30
60
90
120
150
SUPPLY CURRENT (mA)
POWER (mW)
6275 TA15
Figure 6. Composite Amplifier Closed-Loop
Gain/Phase vs Frequency
Figure 7. Composite Amplifier Supply
Current and Total Power Dissipation
LT6274/ LT6275 85 Package 5‘» 4H 4 LE Vii}; 7E7 LJA NOTE \ DLMENSLONSARE w MLLL 2 DRAWWG NOT TU SCALE 3 DLMENSLONSARELNCLDSLVEOFPLATLNG 4 DLMENSLONSARE EXCLUSWE DF MOLD FL 5 MOLD FLASH SHALL NOT EXCEED 0254‘" 5 JEDEC PACKAGE REFERENCE ‘5 M0493 17
LT6274/LT6275
17
6275fa
For more information www.linear.com/LT6275
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/product/LT6274#packaging for the most recent package drawings.
1.50 – 1.75
(NOTE 4)
2.80 BSC
0.30 – 0.45 TYP
5 PLCS (NOTE 3)
DATUM ‘A’
0.09 – 0.20
(NOTE 3) S5 TSOT-23 0302
PIN ONE
2.90 BSC
(NOTE 4)
0.95 BSC
1.90 BSC
0.80 0.90
1.00 MAX 0.01 – 0.10
0.20 BSC
0.30 – 0.50 REF
NOTE:
1. DIMENSIONS ARE IN MILLIMETERS
2. DRAWING NOT TO SCALE
3. DIMENSIONS ARE INCLUSIVE OF PLATING
4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR
5. MOLD FLASH SHALL NOT EXCEED 0.254mm
6. JEDEC PACKAGE REFERENCE IS MO-193
3.85 MAX
0.62
MAX
0.95
REF
RECOMMENDED SOLDER PAD LAYOUT
PER IPC CALCULATOR
1.4 MIN
2.62 REF
1.22 REF
S5 Package
5-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1635)
LT6274/LT6275 18
LT6274/LT6275
18
6275fa
For more information www.linear.com/LT6275
PACKAGE DESCRIPTION
MSOP (MS8) 0213 REV G
0.53 ±0.152
(.021 ±.006)
SEATING
PLANE
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
0.18
(.007)
0.254
(.010)
1.10
(.043)
MAX
0.22 – 0.38
(.009 – .015)
TYP
0.1016 ±0.0508
(.004 ±.002)
0.86
(.034)
REF
0.65
(.0256)
BSC
0° – 6° TYP
DETAIL “A”
DETAIL “A”
GAUGE PLANE
1 2 34
4.90 ±0.152
(.193 ±.006)
8765
3.00 ±0.102
(.118 ±.004)
(NOTE 3)
3.00 ±0.102
(.118 ±.004)
(NOTE 4)
0.52
(.0205)
REF
5.10
(.201)
MIN
3.20 – 3.45
(.126 – .136)
0.889 ±0.127
(.035 ±.005)
RECOMMENDED SOLDER PAD LAYOUT
0.42 ± 0.038
(.0165 ±.0015)
TYP
0.65
(.0256)
BSC
MS8 Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1660 Rev G)
Please refer to http://www.linear.com/product/LT6275#packaging for the most recent package drawings.
LT6274/ LT6275 19
LT6274/LT6275
19
6275fa
For more information www.linear.com/LT6275
REVISION HISTORY
REV DATE DESCRIPTION PAGE NUMBER
A 12/17 Added LT6274
Updated Power Dissipation section
All
13
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog
Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications
subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
LT6274/LT6275 OUTPUT RESPONSE (w izi‘u‘zaasey‘ 20 SEGLc‘ES
LT6274/LT6275
20
6275fa
ANALOG DEVICES, INC. 2017
LT 1217 REV A • PRINTED IN USA
www.linear.com/LT6275
For more information www.linear.com/LT6275
RELATED PARTS
PART NUMBER DESCRIPTION COMMENTS
LT1351/LT1352/LT1353 Single/Dual/Quad 3MHz, 200V/µs, C-Load Amplifiers 250µA Supply Current, 600µV Max VOS, 5V to 30V Supply Operation
LT1354/LT1355/LT1356 Single/Dual/Quad 12MHz, 400V/μs, C-Load Amplifiers 1mA Supply Current, 800µV Max VOS, 5V to 30V Supply Operation
LT1357/LT1358/LT1359 Single/Dual/Quad 25MHz, 600V/μs, C-Load Amplifiers 2mA Supply Current, 600µV Max VOS, 5V to 30V Supply Operation
LT1360/LT1361/LT1362 Single/Dual/Quad 50MHz, 800V/μs, C-Load Amplifiers 4mA Supply Current, 1mV Max VOS, 5V to 30V Supply Operation
LT1363/LT1364/LT1365 Single/Dual/Quad 70MHz, 1000V/μs, C-Load Amplifiers 6.3mA Supply Current, 1.5mV Max VOS, 5V to 30V Supply Operation
LT1812/LT1813/LT1814 Single/Dual/Quad 100MHz, 750V/μs Op Amps 3mA Supply Current, 1.5mV Max VOS, 4V to 11V Supply Operation
LTC6261/LTC6262/LTC6263 Single/Dual/Quad 30MHz, 7V/µs Op Amps 240µA Supply Current, 400µV Max VOS, 1.8V to 5.25V Supply Operation
LTC6246/LTC6247/LTC6248 Single/Dual/Quad 180MHz, 90V/µs Op Amps 0.95mA Supply Current, 500µV Max VOS, 2.5V to 5.25V Supply Operation
LTC6252/LTC6253/LTC6254 Single/Dual/Quad 720MHz, 280V/µs Op Amps 3.3mA Supply Current, 350µV Max VOS, 2.5V to 5.25V Supply Operation
TYPICAL APPLICATION
100pF
10µF
OUTIN +
LT1012
+
LTC2054HV
LTC2756
RCOM
RIN
ROFS REF
RFB
IOUT1
VOUT
IOUT2
GND
VDD
LDAC
CLR
VOSADJ
GEADJ
M-SPAN
S0
S1
S2
10k
1µF
15V
–15V
6275 TA13
0.1µF
12V
LTC6655-5
10k
10k
14
23
25
4
19
20
21
22
17
CS/LD SDI SCK SRO
1211109
SPI BUS
1k
27, 28
26
2351
7
6, 8, 13,
15, 16, 24
10k 5V
–5V
+
LTC6240HV
5V
–5V
+
1/2 LT6275
15V
–15V
1k
10Ω
CCOMP
5pF
1k
4.02k
1µF
Composite Amplifier Provides 18-Bit Precision and Fast Settling
DAC with Composite Amplifier Output Response
(Varying Compensation Capacitance)
C
COMP
100pF
68pF
30pF
22pF
15pF
10pF
TIME (µs)
–2
–1
0
1
2
3
4
5
6
7
–10
–8
–6
–4
–2
0
2
4
6
8
10
12
14
OUTPUT RESPONSE (V)
6275 TA14

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